AD9764(Rev_B) 데이터 시트보기 (PDF) - Analog Devices

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AD9764
(Rev.:Rev_B)

14-Bit, 125 MSPS TxDAC® D/A Converter

Analog Devices 

AD9764

AVDD

AVDD

1.2V

AD1580

OPTIONAL

BANDLIMITING

CAPACITOR

REFLO

COMP1 AVDD

RFB

VDD

OUT1

AD7524 VREF

OUT2

AGND

DB7–DB0

0.1V TO 1.2V

RSET

IREF =

VREF/RSET

+1.2V REF

REFIO

FS ADJ

AD9764

50pF

CURRENT

SOURCE

ARRAY

Figure 25. Single-Supply Gain Control Circuit

The second method may be used in a dual-supply system in

which the common-mode voltage of REFIO is fixed, and IREF is

varied by an external voltage, VGC, applied to RSET via an ampli-

fier. An example of this method is shown in Figure 26 in which

the internal reference is used to set the common-mode voltage

of the control amplifier to 1.20 V. The external voltage, VGC, is

referenced to ACOM and should not exceed 1.2 V. The value of

RSET is such that IREFMAX and IREFMIN do not exceed 62.5 µA

and 625 µA, respectively. The associated equations in Figure 26

can be used to determine the value of RSET.

OPTIONAL

BANDLIMITING

CAPACITOR

AVDD

REFLO

COMP1 AVDD

+1.2V REF

50pF

REFIO

CURRENT

1␮F

FS ADJ

SOURCE

ARRAY

RSET

IREF

AD9764

VGC

IREF = (1.2–VGC)/RSET

WITH VGC < VREFIO AND 62.5␮A Յ IREF Յ 625A

Figure 26. Dual-Supply Gain Control Circuit

In some applications, the user may elect to use an external

control amplifier to enhance the multiplying bandwidth,

distortion performance and/or settling time. External amplifiers

capable of driving a 50 pF load such as the AD817 are suitable

for this purpose. It is configured in such a way that it is in

parallel with the weaker internal reference amplifier as shown in

Figure 27. In this case, the external amplifier simply overdrives

the weaker reference control amplifier. Also, since the internal

control amplifier has a limited current output, it will sustain no

damage if overdriven.

EXTERNAL

CONTROL AMPLIFIER

VREF

INPUT

RSET

REFLO

+1.2V REF

REFIO

FS ADJ

AD9764

AVDD

COMP1 AVDD

50pF

CURRENT

SOURCE

ARRAY

Figure 27. Configuring an External Reference Control

Amplifier

ANALOG OUTPUTS

The AD9764 produces two complementary current outputs,

IOUTA and IOUTB, which may be configured for single-end

or differential operation. IOUTA and IOUTB can be converted into

complementary single-ended voltage outputs, VOUTA and

VOUTB, via a load resistor, RLOAD, as described in the DAC

Transfer Function section by Equations 5 through 8. The

differential voltage, VDIFF, existing between VOUTA and VOUTB

can also be converted to a single-ended voltage via a transformer

or differential amplifier configuration.

Figure 28 shows the equivalent analog output circuit of the

AD9764 consisting of a parallel combination of PMOS differen-

tial current switches associated with each segmented current

source. The output impedance of IOUTA and IOUTB is determined

by the equivalent parallel combination of the PMOS switches

and is typically 100 kΩ in parallel with 5 pF. Due to the na-

ture of a PMOS device, the output impedance is also slightly

dependent on the output voltage (i.e., VOUTA and VOUTB) and, to

a lesser extent, the analog supply voltage, AVDD, and full-scale

current, IOUTFS. Although the output impedance’s signal depen-

dency can be a source of dc nonlinearity and ac linearity (i.e.,

distortion), its effects can be limited if certain precautions are

noted.

AD9764

AVDD

IOUTA

RLOAD

IOUTB

RLOAD

Figure 28. Equivalent Analog Output Circuit

IOUTA and IOUTB also have a negative and positive voltage compli-

ance range. The negative output compliance range of –1.0 V is

set by the breakdown limits of the CMOS process. Operation

beyond this maximum limit may result in a breakdown of the

output stage and affect the reliability of the AD9764. The posi-

tive output compliance range is slightly dependent on the full-

scale output current, IOUTFS. It degrades slightly from its nominal

REV. B

–11–

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